Arcam-P7-pwr-sm维修电路图 手册.pdf

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1、P7 FMJ P7 7-Channel Amplifi er Service Manual ARCAMARCAM Issue 1.0 RadioFans.CN Contents List Section Issue Technical specifications ! Technical specification - ! Rear panel silk screen - Amplifier board L924 ! Circuit description - ! Component overlay 1.0 ! Parts list 1.1 ! Circuit diagrams 1.1 Con

2、troller board L925 ! Circuit description - ! Component overlay 1.0 ! Parts list 1.2 ! Circuit diagrams 1.2 Transformer specifications ! L911TX 1.0 ! L912TX 1.0 ! L920TX 1.0 ! L921TX 1.0 Mechanical ! General assembly parts list - ! Assembly diagrams Front panel - TX tray - - Rear panel - Chassis - Ra

3、dioFans.CN Technical Specifications Technical Specifications All measurements are with 230V/50Hz mains power Continuous output power All channels driven, 20Hz 20Khz, 8 ohm 150W per channel 1.05kW total All channels driven, 20Hz 20kHz, 4 ohm 230W per channel 1.62kW total One or two channels driven at

4、 1kHz, 8 ohm 160W per channel One or two channels driven at 1kHz, 4 ohm 250W per channel One or two channels driven at 1kHz, 3.2 ohm 300W per channel Peak output current capability 25A per channel Total harmonic distortion At any level up to rated power, into 4 or 8 ohms 0.05% (20Hz 20kHz) Typically

5、 0.005% at 1kHz Frequency response +-0.2dB (20Hz 20 kHz) -1dB at 1Hz and 100kHz Residual hum and noise Referenced to full power -122dB, 20Hz 20kHz, unweighted Voltage gain x 28.3 (1V input gives 100W/8 ohm output) Input impedance 22k ohm in parallel with 470pF Output impedance 50m Ohm at 20Hz, 1kHz

6、120m ohm at 20kHz Power requirements 115V or 230VAC, 50/60Hz, 3kW maximum via heavy duty IEC mains inlet A soft start system eliminates large inrush currents at switch on Dimensions W430 x D450 x H180 mm Weight 31kg (68 Ib) nett 35kg (77 Ib) packed 50 60 Hz 3700 VA MAX SERIAL No. LABEL CAUTION SHOCK

7、 HAZARD, DO NOT OPEN. ACHTUNG VOR OEFFNEN DES GERAETES NETZSTECKER ZIEHENNKK Amplifier Board L924 Contents ! Circuit description ! Component overlay ! Parts list ! Circuit diagrams P7 Amplifier Module Circuit Description Refer to L924 circuit diagrams Introduction L924 is the power amplifier module

8、for the P7 multichannel amplifier. There are 7 identical modules in the P7. The circuit design is based on the A85 / A32 output stage topology. The main features of the amplifier module are as follows: Preset THX gain (29dB closed loop gain). 0dBV input signal corresponds to 100 watts into 8 output

9、power Capable of producing 150 watts of sinusoidal output power into an 8 resistive load (with greater than 250W into 3.2 subject to thermal dissipation limits) Relay coupled output for silent power on / off and load protection Opto-isolated fault and control lines to the microprocessor PCB (to avoi

10、d hum loops and instability, to improve EMC performance and crosstalk) DC coupled signal path with integrating servo to remove residual DC errors Instantaneous load protection Mono block design (each channel is electrically isolated from all others and has independent power supply windings on the ma

11、ins transformer) Integrated modular heatsink for good thermal performance and ease of assembly / servicing Low harmonic and intermodulation distortion Flat frequency response Fast (and symmetrical) slew rate High damping factor Unconditionally stable into loads of up to 90 phase angle Sheet 1 The in

12、put to the amplifier is connected via SK103. The 2 phono sockets are connected in parallel to allow daisy- chaining of amplifier modules. R104 provides a DC leakage path to the chassis (i.e. mains power earth) to prevent small transformer leakage currents causing the electrical 0V of the amplifier t

13、o rise significantly above mains earth potential. C104 provides an EMC coupling between the local input ground and the chassis to reduce common mode RF noise. Star point SP101 connects the differently named electrical 0V nets at a single point. This is to ensure the correct wiring topology of the gr

14、ound connections on the printed circuit board. SP101 provides a good common ground reference point when making voltage measurements on the PCB. Note that 0V_DIG is not connected to SP101, as this is the microprocessor ground. Relay RLY101 connects the output of the amplifier to the load via socket S

15、K105. L101 and R103 form part of a Zobel network to decouple the load at high frequencies to ensure amplifier stability into capacitive loads. Note that signals 6 through 9 are open collector outputs, active low, referred to 0V_DIG with no pull-up resistors. This is because they are wire ORd on the

16、microprocessor PCB (L925), where the pull-up resistors to +5V digital are located. The line NFB provides for a portion of the negative feedback of the amplifier to be taken on the load side of RLY101. The components that allow for this (R236 thru R239) are not presently fitted, meaning that RLY101 i

17、s not included in the feedback loop. SK104 connects to the microcontroller PCB. Note that all signals on this connector are electrically isolated from the amplifier circuit itself, via either opto isolators or the relay coil of RLY101. The 10- pin connector has the following signals: SK104 Pin Type

18、Name Description 1 GND 0V_DIG Microprocessor ground return 2 PSU +24V_DIG +24 volt digital power supply (referred to 0V_DIG only) for relay coil RLY101 3 MUTE Not used 4 I/P OUT_RLY Relay drive for the output relay RLY101 (LOW = output relay ON) 5 Not used 6 O/P THERMPR OT Open collector thermal fau

19、lt signal (LOW = FAULT) 7 O/P VIPROT Open collector short circuit fault signal (LOW = FAULT) 8 O/P DCPROT Open collector DC fault signal (LOW = FAULT) 9 O/P FAULT Open collector overall fault signal (LOW = FAULT) 10 Not used Sheet 2 Port INPUT connects the input of the amplifier, referred to 0V_SIG,

20、 which is the precision signal ground reference. Zener diodes DZ202 and DZ203 limit the input signal amplitude to approximately 5.3Vpk. This is to prevent damage to the input of op- amp IC200, due to a leaky source signal or electrostatic discharge. R223, R228 and C210 form a passive 1st order low p

21、ass filter with a 3dB corner frequency of roughly 330kHz to prevent ultrasonic signals from entering the circuit and possibly causing damage. The main amplifier circuit is a classic current feedback design. IC200A is configured as a non-inverting amplifier with a gain of 2. Its purpose is to provide

22、 current outputs (via its power supply pins) and a current input (via its output pin). This forms the voltage to current (transimpedance) conversion and phase splitting necessary to drive the voltage gain stage. The current feedback occurs because when IC200 drives its 44 load to ground, the power s

23、upply pin currents are half-wave rectified versions of the drive current of the amplifier. This causes voltage gain, which is buffered and passed on to the outputs. The feedback from the output to pin 1 of IC200 acts to reduce the gain of the amplifier; when this current is roughly equal to the curr

24、ent required to drive the input signal into 44, equilibrium is reached and the closed loop gain is defined. The output stage provides the vast majority of the current required to drive the 44 signals to ground. The op-amp only provides a very small error current sufficient to give the required volta

25、ge magnification. Transistors TR204 and TR203 are wired as cascodes (common base amplifiers). Their purpose is to provide IC200 with 15V power supply rails, whilst allowing IC200s power supply pin currents to pass through them to the NPN and PNP current mirrors. The resistor, zener diode and capacit

26、or circuits on the bases of TR204 and TR203 are to provide a controlled ramp up during power on, a stable power supply voltage and good local HF decoupling. Transistors TR200, TR201 and TR202 form a PNP Wilson current mirror. Likewise TR205, TR207 and TR206 form an NPN Wilson current mirror. The out

27、puts of these two current mirrors are connected together via the bias network around TR212. The two current mirrors combine to provide a very high-gain current to voltage (transresistance) gain stage, which provides all the voltage gain of the amplifier (roughly 80dB at low frequency). C205, C207, R

28、221 and R222 provide the loop compensation for the amplifier. They combine to produce an open-loop pole at roughly 10kHz and a corresponding open-loop zero around 500kHz. This allows for good time domain performance and clean square wave reproduction. The amplifier is designed to be critically dampe

29、d. There should be no ringing or overshoot apparent on the output signal when a (small) step function is applied to the input. Diodes D200 and D202 act to limit the current through TR202 and TR206 in the event of a fault condition. When the input current exceeds 14mA the diodes conduct and the trans

30、resistance stage becomes a constant current source, killing the open loop gain and preventing damage to the transistors. Resistors R219 and R220 decouple the supplies for the amplifier gain stages from the main power rails. This is to permit the bootstrap circuit to modulate these supplies, increasi

31、ng efficiency. The bootstrap will be described in more detail later. TR212 provides a 4.7V bias voltage to allow the following pre-driver stage to operate in class A. It also acts as a VBE multiplier for TR209 and TR214 to maintain an approximately constant current as the ambient temperature inside

32、the box changes. TR209 and TR214 form a class A pre-driver emitter follower stage to boost the current gain and isolate the transresistance stage from the output transistors. This is important to keep the loop gain of the amplifier high and thus minimise distortion. TR208 and TR213 act as a current

33、limit (roughly 30mA) to prevent the destruction of TR209 and TR214 in a fault condition. R247, R248, R249 and R250 are to loosely decouple the emitters of TR209 and TR214 from the output stage. This is very important. The output devices (Sanken power Darlingtons) have inbuilt temperature compensatin

34、g diodes which control the bias voltage to their bases. Each output device has a 150 resistor so that the inbuilt diodes can accurately control quiescent VBE and hence collector current as the output power and device temperature varies. Preset potentiometer RV200 adjusts the quiescent current. NB: E

35、nsure that the amplifier has fully warmed up before adjusting the quiescent current. D201 protects the output devices from destruction in the event of the preset potentiometer going open circuit. PL200 allows the test engineer to measure the bias voltage (and thus collector current). C217, C218, C22

36、0 and C221 provide local HF stability around the output transistors to prevent parasitic oscillation. D204 and D205 are catch diodes to reduce the effects of induced back-EMF in the loudspeaker load. R254 and C223 form part of the Zobel network that ensures the amplifier sees a constant load of roug

37、hly 4.7 at very high frequencies. This helps to improve stability and reduce HF output noise. C208 and C209 provide local high frequency decoupling for the output devices. IC200B forms the DC integrating servo. Its purpose is to remove residual DC errors due to slight device mismatch and component t

38、olerances. It is configured as an inverting integrator with a time constant of 0.47 seconds. Any positive DC offset at the output of the amplifier will cause the output of the op-amp to go negative, increasing the current in the negative supply pin and thus pulling the output down to ground (and vic

39、e versa). D203 protects the inverting input of IC200B in a fault condition. The bootstrap circuit consists of C213, C214, R241, R242, R219 and R220. The purpose of the bootstrap is to allow the output voltage swing to modulate the power supply rails of the input and voltage gain stages. This allows

40、this circuits power supply voltage to exceed the main power rails connected to the output devices, allowing the driver stage to fully drive the output and thus give the best thermal efficiency. The bottom of R219 sees a peak-to-peak voltage swing of approximately 15 volts at full output power (i.e.

41、it goes 7.5 volts above the rail at the peak of the cycle). The top of R220 should see the same voltage swing. Sheet 3 This sheet contains the protection circuits and interface to the microprocessor signals. TR309, TR305 and their associated components form the instantaneous load protection circuit

42、for the output transistors. They sense the voltage across the 0.22 emitter resistors (hence emitter current) and the collector-emitter voltage, cutting off the base drive to the output transistors when the collector current or device power dissipation exceeds a preset limit. The protection circuit i

43、s designed to allow large (unrestricted) currents into loads of 3 and above but limit the current into a short circuit or very low impedance load. C318, C319, R335 and R336 form a 2.2ms time constant, which will allow larger transients of current delivery for a few milliseconds, to ensure that the a

44、mplifier has a sufficiently large transient capability to drive difficult loudspeaker loads with a music signal. TR311 also turns on when the protection circuit activates. This switches on optocoupler IC300B causing a fault signal to be transmitted to the microcontroller. The microcontroller will th

45、en switch off the output relay to protect the amplifier. TR310, TR302 and their associated components form the DC offset detection circuit. A positive DC offset at the output will turn on TR310. A negative DC offset at the output will turn on TR302, thus causing TR313 to turn on. In either case opto

46、coupler IC300A is switched on causing a fault signal to be transmitted to the microcontroller. The microcontroller will then switch off the output relay to protect the loudspeaker voice coils from overheating. Thermistor TH300 is connected to the positive supply rail, adjacent to the collector leg o

47、f one of the power output devices. This allows it to sense the collector temperature of the output device. Its impedance when cool is low, typically a few hundred ohms. In the event of a thermal overload (above 110C), TH300 will go to a high impedance state. This will turn on TR301, which then turns

48、 on TR300, causing optocoupler IC300D to switch on, sending a fault signal to the microcontroller. The microcontroller will then switch off the output relay until such time as the unit has cooled down to an acceptable level (80C or so). TR301 is configured with a small amount of hysterisis (positive

49、 feedback) to ensure a clean signal is transmitted to the microprocessor via IC300D. Optocoupler IC300C is connected in series with the 3 optocouplers mentioned above, producing an overall fault signal. This is so that the microcontroller can determine in which module the fault has occurred, permitting selective control of the outpu